Antennaless Wireless Device Capable of Operation in Multiple Frequency Regions

ABSTRACT

A radiating system comprises a radiating structure, first and second external ports, and a radiofrequency system. The radiating structure comprises a ground plane layer including a connection point, a single radiation booster including a connection point, and a first internal port defined between the connection points of the single radiation booster and the ground plane layer. The first and second external ports each provide operation in at least one frequency band. The radiofrequency system includes a first port connected to the first internal port of the radiating structure, and second and third ports respectively connected to the first and second external ports.

CROSS REFERENCE TO RELATED APPLICATIONS

This application is a continuation of U.S. patent application Ser. No.16/941,075, filed on Jul. 28, 2020, which is a continuation of U.S.patent application Ser. No. 16/275,792, filed on Feb. 14, 2019, now U.S.Pat. No. 10,763,585, issued on Sep. 1, 2020, which is a continuation ofU.S. patent application Ser. No. 15/927,497, filed on Mar. 21, 2018, nowU.S. Pat. No. 10,249,952, issued on Apr. 2, 2019, which is acontinuation of U.S. patent application Ser. No. 15/131,920, filed onApr. 18, 2016, now U.S. Pat. No. 9,960,490, issued on May 1, 2018, whichis a continuation of U.S. patent application Ser. No. 14/257,511, filedon Apr. 21, 2014, now U.S. Pat. No. 9,350,070, issued on May 24, 2016,which is a continuation of U.S. patent application Ser. No. 13/530,704filed Jun. 22, 2012, now U.S. Pat. No. 8,736,497, issued on May 27,2014, which is a continuation of U.S. patent application Ser. No.12/669,928, filed on Feb. 22, 2010, now U.S. Pat. No. 8,327,615, issuedon Aug. 7, 2012, which is a National Stage Entry of PCT/EP2009/005578,filed on Jul. 31, 2009. In addition, U.S. patent application Ser. No.12/669,928 claims priority from U.S. Provisional Application Nos.61/086,838, filed on Aug. 7, 2008 and 61/142,523, filed on Jan. 5, 2009.The entire contents of each of the aforementioned applications arehereby incorporated by reference.

FIELD OF THE INVENTION

The present invention relates to the field of wireless handheld devices,and generally to wireless portable devices which require thetransmission and reception of electromagnetic wave signals.

BACKGROUND

Wireless handheld or portable devices typically operate one or morecellular communication standards and/or wireless connectivity standards,each standard being allocated in one or more frequency bands, and saidfrequency bands being contained within one or more regions of theelectromagnetic spectrum.

For that purpose, a space within the wireless handheld or portabledevice is usually dedicated to the integration of a radiating system.The radiating system is, however, expected to be small in order tooccupy as little space as possible within the device, which then allowsfor smaller devices, or for the addition of more specific equipment andfunctionality into the device. At the same time, it is sometimesrequired for the radiating system to be flat since this allows for slimdevices or in particular, for devices which have two parts that can beshifted or twisted against each other.

Many of the demands for wireless handheld or portable devices alsotranslate to specific demands for the radiating systems thereof.

A typical wireless handheld device must include a radiating systemcapable of operating in one ore more frequency regions with goodradioelectric performance (such as for example in terms of inputimpedance level, impedance bandwidth, gain, efficiency, or radiationpattern). Moreover, the integration of the radiating system within thewireless handheld device must be correct to ensure that the wirelessdevice itself attains a good radioelectric performance (such as forexample in terms of radiated power, received power, or sensitivity).

This is even more critical in the case in which the wireless handhelddevice is a multifunctional wireless device. Commonly-owned patentapplications WO2008/009391 and US2008/0018543 describe a multifunctionalwireless device. The entire disclosure of said application numbersWO2008/009391 and US2008/0018543 are hereby incorporated by reference.

For a good wireless connection, high gain and efficiency are furtherrequired. Other more common design demands for radiating systems are thevoltage standing wave ratio (VSWR) and the impedance which is supposedto be about 50 ohms.

Other demands for radiating systems for wireless handheld or portabledevices are low cost and a low specific absorption rate (SAR).

Furthermore, a radiating system has to be integrated into a device or inother words a wireless handheld or portable device has to be constructedsuch that an appropriate radiating system may be integrated thereinwhich puts additional constraints by consideration of the mechanicalfit, the electrical fit and the assembly fit.

Of further importance, usually, is the robustness of the radiatingsystem which means that the radiating system does not change itsproperties upon smaller shocks to the device.

A radiating system for a wireless device typically includes a radiatingstructure comprising an antenna element which operates in combinationwith a ground plane layer providing a determined radioelectricperformance in one or more frequency regions of the electromagneticspectrum. This is illustrated in FIG. 17, in which it is shown aconventional radiating structure 1700 comprising an antenna element 1701and a ground plane layer 1702. Typically, the antenna element has adimension close to an integer multiple of a quarter of the wavelength ata frequency of operation of the radiating structure, so that the antennaelement is at resonance at said frequency and a radiation mode isexcited on said antenna element.

Although the radiating structure is usually very efficient at theresonance frequency of the antenna element and maintains a similarperformance within a frequency range defined around said resonancefrequency (or resonance frequencies), outside said frequency range theefficiency and other relevant antenna parameters deteriorate with anincreasing distance to said resonance frequency.

Furthermore, the radiating structure operating at a resonance frequencyof the antenna element is typically very sensitive to external effects(such as for instance the presence of plastic or dielectric covers thatsurround the wireless device), to components of the wireless device(such as for instance, but not limited to, a speaker, a microphone, aconnector, a display, a shield can, a vibrating module, a battery, or anelectronic module or subsystem) placed either in the vicinity of, oreven underneath, the antenna element, and/or to the presence of the userof the wireless device.

Any of the above mentioned aspects may alter the current distributionand/or the electromagnetic field distribution of a radiation mode of theantenna element, which usually translates into detuning effects,degradation of the radioelectric performance of the radiating structureand/or the radioelectric performance wireless device, and/or greaterinteraction with the user (such as an increased level of SAR).

A further problem associated to the integration of the radiatingstructure, and in particular to the integration of the antenna element,in a wireless device is that the volume dedicated for such anintegration has continuously shrunk with the appearance of new smallerand/or thinner form factors for wireless devices, and with theincreasing convergence of different functionality in a same wirelessdevice.

Some techniques to miniaturize and/or optimize the multiband behavior ofan antenna element have been described in the prior art. However, theradiating structures therein described still rely on exciting aradiation mode on the antenna element.

For example, commonly-owned co-pending patent application US2007/0152886describes a new family of antennas based on the geometry ofspace-filling curves.

Also, commonly-owned co-pending patent application US2008/0042909relates to a new family of antennas, referred to as multilevel antennas,formed by an electromagnetic grouping of similar geometrical elements.The entire disclosures of the aforesaid application numbersUS2007/0152886 and US2008/0042909 are hereby incorporated by reference.

Some other attempts have focused on antenna elements not requiring acomplex geometry while still providing some degree of miniaturization byusing an antenna element that is not resonant in the one or morefrequency ranges of operation of the wireless device.

For example, WO2007/128340 discloses a wireless portable devicecomprising a non-resonant antenna element for receiving broadcastsignals (such as, for instance, DVB-H, DMB, T-DMB or FM). The wirelessportable device further comprises a ground plane layer that is used incombination with said antenna element. Although the antenna element hasa first resonance frequency above the frequency range of operation ofthe wireless device, the antenna element is still the main responsiblefor the radiation process and for the electromagnetic performance of thewireless device. This is clear from the fact that no radiation mode canbe excited on the ground plane layer because the ground plane layer iselectrically short at the frequencies of operation (i.e., its dimensionsare much smaller than the wavelength).

With such limitations, while the performance of the wireless portabledevice may be sufficient for reception of electromagnetic wave signals(such as those of a broadcast service), the antenna element could notprovide an adequate performance (for example, in terms of input returnlosses or gain) for a cellular communication standard requiring also thetransmission of electromagnetic wave signals.

Commonly-owned patent application WO2008/119699 describes a wirelesshandheld or portable device comprising a radiating system capable ofoperating in two frequency regions. The radiating system comprises anantenna element having a resonance frequency outside said two frequencyregions, and a ground plane layer. In this wireless device, while theground plane layer contributes to enhance the electromagneticperformance of the radiating system in the two frequency regions ofoperation, it is still necessary to excite a radiation mode on theantenna element. In fact, the radiating system relies on therelationship between a resonance frequency of the antenna element and aresonance frequency of the ground plane layer in order for the radiatingsystem to operate properly in said two frequency regions.

The entire disclosure of the aforesaid application number WO2008/119699is hereby incorporated by reference.

Some further techniques to enhance the behavior of an antenna elementrelate to optimizing the geometry of a ground plane layer associated tosaid antenna element. For example, commonly-owned co-pending patentapplication U.S. Ser. No. 12/033,446 describes a new family of groundplane layers based on the geometry of multilevel structures and/orspace-filling curves. The entire disclosure of the aforesaid applicationnumber U.S. Ser. No. 12/033,446 is hereby incorporated by reference.

Another limitation of current wireless handheld or portable devicesrelates to the fact that the design and integration of an antennaelement for a radiating structure in a wireless device is typicallycustomized for each device. Different form factors or platforms, or adifferent distribution of the functional blocks of the device will forceto redesign the antenna element and its integration inside the devicealmost from scratch.

For at least the above reasons, wireless device manufacturers regard thevolume dedicated to the integration of the radiating structure, and inparticular the antenna element as being a toll to pay in order toprovide wireless capabilities to the handheld or portable device.

SUMMARY

It is an object of the present invention to provide a wireless handheldor portable device (such as for instance but not limited to a mobilephone, a smartphone, a PDA, an MP3 player, a headset, a USB dongle, alaptop computer, a gaming device, a digital camera, a PCMCIA or Cardbus32 card, or generally a multifunction wireless device) which does notrequire an antenna element for the transmission and reception ofelectromagnetic wave signals. Such an antennaless wireless device is yetcapable of operation in two or more frequency regions of theelectromagnetic spectrum with enhanced radioelectric performance,increased robustness to external effects and neighboring components ofthe wireless device, and/or reduced interaction with the user.

Another object of the invention relates to a method to enable theoperation of a wireless handheld or portable device in two or morefrequency regions of the electromagnetic spectrum with enhancedradioelectric performance, increased robustness to external effects andneighboring components of the wireless device, and/or reducedinteraction with the user, without requiring the use of an antennaelement.

Therefore, a wireless device not requiring an antenna element would beadvantageous as it would ease the integration of the radiating structureinto the wireless handheld or portable device. The volume freed up bythe absence of the antenna element would enable smaller and/or thinnerdevices, or even to adopt radically new form factors (such as forinstance elastic, stretchable and/or foldable devices) which are notfeasible today due to the presence of an antenna element.

Furthermore, by eliminating precisely the element that requirescustomization, a standard solution is obtained which only requires minoradjustments to be implemented in different wireless devices.

A wireless handheld or portable device that does not require of anantenna element, yet the wireless device featuring an adequateradioelectric performance in two or more frequency regions of theelectromagnetic spectrum would be an advantageous solution. This problemis solved by an antennaless wireless handheld or portable deviceaccording to the present invention.

An antennaless wireless handheld or portable device according to thepresent invention operates one, two, three, four or more cellularcommunication standards (such as for example GSM 850, GSM 900, GSM 1800,GSM 1900, UMTS, HSDPA, CDMA, W-CDMA, LTE, CDMA2000, TD-SCDMA, etc.),wireless connectivity standards (such as for instance WiFi, IEEE802.11standards, Bluetooth, ZigBee, UWB, WiMAX, WiBro, or other high-speedstandards), and/or broadcast standards (such as for instance FM, DAB,XDARS, SDARS, DVB-H, DMB, T-DMB, or other related digital or analogvideo and/or audio standards), each standard being allocated in one ormore frequency bands, and said frequency bands being contained withintwo, three or more frequency regions of the electromagnetic spectrum.

In the context of this document, a frequency band preferably refers to arange of frequencies used by a particular cellular communicationstandard, a wireless connectivity standard or a broadcast standard;while a frequency region preferably refers to a continuum of frequenciesof the electromagnetic spectrum. For example, the GSM 1800 standard isallocated hi a frequency band from 1710 MHz to 1880 MHz while the GSM1900 standard is allocated in a frequency band from 1850 MHz to 1990MHz. A wireless device operating the GSM 1800 and the GSM 1900 standardsmust have a radiating system capable of operating in a frequency regionfrom 1710 MHz to 1990 MHz. As another example, a wireless deviceoperating the GSM 1800 standard and the UMTS standard (allocated in afrequency band from 1920 MHz to 2170 MHz), must have a radiating systemcapable of operating in two separate frequency regions.

The antennaless wireless handheld or portable device according to thepresent invention may have a candy-bar shape, which means that itsconfiguration is given by a single body. It may also have a two-bodyconfiguration such as a clamshell, flip-type, swivel-type or sliderstructure. In some other cases, the device may have a configurationcomprising three or more bodies. It may further or additionally have atwist configuration in which a body portion (e.g. with a screen) can betwisted (i.e., rotated around two or more axes of rotation which arepreferably not parallel). Also, the present invention makes it possiblefor radically new form factors, such as for example devices made ofelastic, stretchable and/or foldable materials.

For a wireless handheld or portable device which is slim and/or whoseconfiguration comprises two or more bodies, the requirements on maximumheight of the antenna element are very stringent, as the maximumthickness of each of the two or more bodies of the device may be limitedto 5, 6, 7, 8 or 9 mm. The technology disclosed herein makes it possiblefor a wireless handheld or portable device to feature an enhancedradioelectric performance without requiring an antenna element, thussolving the space constraint problems associated to such devices.

In the context of the present document a wireless handheld or portabledevice is considered to be slim if it has a thickness of less than 14mm, 13 mm, 12 mm, 11 mm, 10 mm, 9 mm or 8 mm.

According to the present invention, an antennaless wireless handheld orportable device advantageously comprises at least five functionalblocks: a user interface module, a processing module, a memory module, acommunication module and a power management module. The user interfacemodule comprises a display, such as a high resolution LCD, OLED orequivalent, and is an energy consuming module, most of the energy draincoming typically from the backlight use. The user interface module mayalso comprise a keypad and/or a touchscreen, and/or an embedded styluspen. The processing module, that is a microprocessor or a CPU, and theassociated memory module are also major sources of power consumption.The fourth module responsible of energy consumption is the communicationmodule, an essential part of which is the radiating system. The powermanagement module of the antennaless wireless handheld or portabledevice includes a source of energy (such as for instance, but notlimited to, a battery or a fuel cell) and a power management circuitthat manages the energy of the device.

In accordance with the present invention, the communication module ofthe antennaless wireless handheld or portable device includes aradiating system capable of transmitting and receiving electromagneticwave signals in at least two frequency regions of the electromagneticspectrum: a first frequency region and a second frequency region,wherein preferably the highest frequency of the first frequency regionis lower than the lowest frequency of the second frequency region. Saidradiating system comprises a radiating structure comprising: at leastone ground plane layer capable of supporting at least one radiationmode, the at least one ground plane layer including at least oneconnection point; at least one radiation booster to coupleelectromagnetic energy from/to the at least one ground plane layer,the/each radiation booster including a connection point; and at leastone internal port. The/each internal port is defined between theconnection point of the/each radiation booster and one of the at leastone connection points of the at least one ground plane layer. Theradiating system further comprises a radiofrequency system, and anexternal port.

In some cases, the radiating system of an antennaless wireless handheldor portable device comprises a radiating structure consisting of: atleast one ground plane layer including at least one connection point; atleast one radiation booster, the/each radiation booster including aconnection point; and at least one internal port.

The radiofrequency system comprises a port connected to each of the atleast one internal ports of the radiating structure (i.e., as many portsas there are internal ports in the radiating structure), and a portconnected to the external port of the radiating system. Saidradiofrequency system modifies the impedance of the radiating structure,providing impedance matching to the radiating system in the at least twofrequency regions of operation of the radiating system.

In this text, a port of the radiating structure is referred to as aninternal port; while a port of the radiating system is referred to as anexternal port. In this context, the terms “internal” and “external” whenreferring to a port are used simply to distinguish a port of theradiating structure from a port of the radiating system, and carry noimplication as to whether a port is accessible from the outside or not.

In some examples, the radiating system is capable of operating in atleast two, three, four, five or more frequency regions of theelectromagnetic spectrum, said frequency regions allowing the allocationof two, three, four, five, six or more frequency bands used in one ormore standards of cellular communications, wireless connectivity and/orbroadcast services.

In some examples, a frequency region of operation (such as for examplethe first and/or the second frequency region) of a radiating system ispreferably one of the following (or contained within one of thefollowing): 824-960 MHz, 1710-2170 MHz, 2.4-2.5 GHz, 3.4-3.6 GHz,4.9-5.875 GHz, or 3.1-10.6 GHz.

In some embodiments, the radiating structure comprises two, three, fouror more radiation boosters, each of said radiation boosters including aconnection point, and each of said connection points defining, togetherwith a connection point of the at least one ground plane layer, aninternal port of the radiating structure.

Therefore, in some embodiments the radiating structure comprises two,three, four or more radiation boosters, and correspondingly two, three,four or more internal ports.

In some examples, a same connection point of the at least one groundplane layer is used to define at least two, three, or even all, internalports—of the radiating structure.

In some examples, the radiating system comprises a second external portand the radiofrequency system comprises an additional port, saidadditional port being connected to said second external port. That is,the radiating system features two external ports.

An aspect of the present invention relates to the use of the groundplane layer of the radiating structure as an efficient radiator toprovide an enhanced radioelectric performance in two or more frequencyregions of operation of the wireless handheld or portable device,eliminating thus the need for an antenna element, and particularly theneed for a multiband antenna element. Different radiation modes of theground plane layer can be advantageously excited when a dimension ofsaid ground plane layer is on the order of, or even larger than, onehalf of the wavelength corresponding to a frequency of operation of theradiating system.

Therefore, in an antennaless wireless device according to the presentinvention, no other parts or elements of the wireless handheld orportable device have significant contribution to the radiation process.

In some embodiments, at least one, two, three, or even all, of saidradiation modes occur at frequencies advantageously located above (i.e.,at a frequency higher than) the first frequency region of operation ofthe wireless handheld or portable device. In some other embodiments, thefrequency of at least one radiation mode of said ground plane layer iswithin said first frequency region.

In some embodiments, at least one, two, or three, radiation modes of theground plane layer is/are advantageously located above the secondfrequency region of operation of the wireless handheld or portabledevice.

A ground plane rectangle is defined as being the minimum-sized rectanglethat encompasses a ground plane layer of the radiating structure. Thatis, the ground plane rectangle is a rectangle whose sides are tangent toat least one point of said ground plane layer.

In some cases, the ratio between a side of the ground plane rectangle,preferably a long side of the ground plane rectangle, and the free-spacewavelength corresponding to the lowest frequency of the first frequencyregion is advantageously larger than a minimum ratio. Some possibleminimum ratios are 0.1, 0.16, 0.2, 0.3, 0.4, 0.5, 0.6, 0.8, 1, 1.2 and1.4. Said ratio may additionally be smaller than a maximum ratio (i.e.,said ratio may be larger than a minimum ratio but smaller than a maximumratio). Some possible maximum ratios are 0.4, 0.5, 0.6, 0.8, 1, 1.2,1.4, 1.6, 2, 3, 4, 5, 6, 8 and 10.

Setting a dimension of the ground plane rectangle, preferably thedimension of its long side, relative to said free-space wavelengthwithin these ranges makes it possible for the ground plane layer tosupport one, two, three or more efficient radiation modes, in which thecurrents flowing on the ground plane layer are substantially aligned andcontribute in phase to the radiation process.

The gain of a radiating structure depends on factors such as itsdirectivity, its radiation efficiency and its input return loss. Boththe radiation efficiency and the input return loss of the radiatingstructure are frequency dependent (even directivity is strictlyfrequency dependent). A radiating structure is usually very efficientaround the frequency of a radiation mode excited in the ground planelayer and maintains a similar radioelectric performance within thefrequency range defined by its impedance bandwidth around saidfrequency. Since the dimensions of the ground plane layer (or those ofthe ground plane rectangle) are comparable to, or larger than, thewavelength at the frequencies of operation of the wireless device, saidradiation mode may be efficient over a broad range of frequencies.

In this text, the expression impedance bandwidth is to be interpreted asreferring to a frequency region over which a wireless handheld orportable device and a radiating system comply with certainspecifications, depending on the service for which the wireless deviceis adapted. For example, for a device adapted to transmit and receivesignals of cellular communication standards, a radiating system having arelative impedance bandwidth of at least 5% (and more preferably notless than 8%, 10%, 15% or 20%) together with an efficiency of not lessthan 30% (advantageously not less than 40%, more advantageously not lessthan 50%) can be preferred. Also, an input return-loss of −3d8 or betterwithin the corresponding frequency region can be preferred.

A wireless handheld or portable device generally comprises one, two,three or more multilayer printed circuit boards (PCBs) on which to carrythe electronics. In a preferred embodiment of an antennaless wirelesshandheld or portable device, the ground plane layer of the radiatingstructure is at least partially, or completely, contained in at leastone of the layers of a multilayer PCB.

In some cases, a wireless handheld or portable device may comprise two,three, four or more ground plane layers. For example a clamshell,flip-type, swivel-type or slider-type wireless device may advantageouslycomprise two PCBs, each including a ground plane layer.

The/Each radiation booster advantageously couples the electromagneticenergy from the radiofrequency system to the ground plane layer intransmission, and from the ground plane layer to the radiofrequencysystem in reception. Thereby the radiation booster boosts the radiationor reception of electromagnetic radiation.

In some examples, the/each radiation booster has a maximum size smallerthan 1/30, 1/40, 1/50, 1/60, 1/80, 0.1/100, 1/140 or even 1/180 timesthe free-space wavelength corresponding to the lowest frequency of thefirst frequency region of operation of the antennaless wireless handheldor portable device.

In some further examples, at least one (such as for instance, one, two,three or more) radiation booster has a maximum size smaller than 1/30,1/40, 1/50, 1/60, 1/80, 1/100, 1/140 or even 1/180 times the free-spacewavelength corresponding to the lowest frequency of the second frequencyregion of operation of said device.

An antenna element is said to be small (or miniature) when it can befitted in a small space compared to a given operating wavelength. Moreprecisely, a radiansphere is usually taken as the reference forclassifying whether an antenna element is small. The radiansphere is animaginary sphere having a radius equal to said operating wavelengthdivided by two times 71 It Therefore, a maximum size of the antennaelement must necessarily be not larger than the diameter of saidradiansphere (i.e., approximately equal to ⅓ of the free-space operatingwavelength) in order to be considered small at said given operatingwavelength.

As established theoretically by H. Wheeler and L. J. Chu in the mid1940's, small antenna elements typically have a high quality factor (Q)which means that most of the power delivered to the antenna element isstored in the vicinity of the antenna element in the form of reactiveenergy rather than being radiated into space. In other words, an antennaelement having a maximum size smaller than ⅓ of the free-space operatingwavelength may be regarded as radiating poorly by a skilled-in-the-artperson.

The/Each radiation booster for a radiating structure according to thepresent invention has a maximum size at least smaller than 1/30 of thefree-space wavelength corresponding to the lowest frequency of the firstfrequency region of operation. That is, the/each radiation booster fitsin an imaginary sphere having a diameter ten (10) times smaller than thediameter of a radiansphere at said same operating wavelength.

Setting the dimensions of the/each radiation booster to such smallvalues is advantageous because the radiation booster substantiallybehaves as a non-radiating element for all the frequencies of the firstand second frequency regions, thus substantially reducing the loss ofenergy into free space due to undesired radiation effects of theradiation booster, and consequently enhancing the transfer of energybetween the radiation booster and the ground plane layer. Therefore, theskilled-in-the-art person could not possibly regard the/each radiationbooster as being an antenna element.

The maximum size of a radiation booster is preferably defined by thelargest dimension of a booster box that completely encloses saidradiation booster, and in which the radiation booster is inscribed.

More specifically, a booster box for a radiation booster is defined asbeing the minimum-sized parallelepiped of square or rectangular facesthat completely encloses the radiation booster and wherein each one ofthe faces of said minimum-sized parallelepiped is tangent to at least apoint of said radiation booster. Moreover, each possible pair of facesof said minimum-size parallelepiped sharing an edge forms an inner angleof 90°.

In those cases in which the radiating structure comprises more than oneradiation booster, a different booster box is defined for each of them.

In some examples, one of the dimensions of a booster box can besubstantially smaller than any of the other two dimensions, or even beclose to zero. In such cases, said booster box collapses to apractically two-dimensional entity. The term dimension preferably refersto an edge between two faces of said parallelepiped.

Additionally, in some of these examples the/each radiation booster has amaximum size larger than 1/1400, 1/700, 1/350, 1/250, 1/180, 1/140 or1/120 times the free-space wavelength corresponding to the lowestfrequency of said first frequency region. Therefore, in some examplesthe/each radiation booster has a maximum size advantageously smallerthan a first fraction of the free-space wavelength corresponding to thelowest frequency of the first frequency region but larger than a secondfraction of said free-space wavelength.

Furthermore, in some of these examples, at least one, two, or threeradiation boosters have a maximum size larger than 1/1400, 1/700, 1/350,1/175, 1/120, or 1/90 times the free-space wavelength corresponding tothe lowest frequency of the second frequency region of operation of theantennaless wireless handheld or portable device.

Setting the dimensions of a radiation booster to be above some certainminimum value is advantageous to obtain a higher level of the real partof the input impedance of the radiating structure (measured at theinternal port of the radiating structure associated to said radiationbooster when disconnected from the radiofrequency system) and in thisway enhance the transfer of energy between said radiation booster andthe ground plane layer.

In some other cases, preferably in combination with the above feature ofan upper bound for the maximum size of a radiation booster although notalways required, to reduce even further the losses in a radiationbooster due to residual radiation effects, said radiation booster isdesigned so that the radiating structure has at the internal port ofsaid radiating structure associated to said radiation booster, whendisconnected from the radiofrequency system, a first resonance frequencyat a frequency much higher than the frequencies of the first frequencyregion of operation. Moreover, said first resonance frequency maypreferably be also much higher than the frequencies of the secondfrequency region of operation. In some examples, a radiation booster hasa dimension substantially close to a quarter of the wavelengthcorresponding to the first resonance frequency at the internal port ofthe radiating structure associated to said radiation booster.

In a preferred example, the radiating structure features at the/eachinternal port, when disconnected from the radiofrequency system, a firstresonance frequency located above (i.e., higher than) the firstfrequency region of operation of the radiating system.

In some examples, for at least some of, or even all, the internal portsof the radiating structure, the ratio between the first resonancefrequency at a given internal port of the radiating structure whendisconnected from the radiofrequency system and the highest frequency ofsaid first frequency region is preferably larger than a certain minimumratio. Some possible minimum ratios are 3.0, 3.4, 3.8, 4.0, 4.2, 4.4,4.6, 4.8, 5.0, 5.2, 5.4, 5.6, 5.8, 6.0, 6.2, 6.6 or 7.0.

In the context of this document, a resonance frequency associated to aninternal port of the radiating structure preferably refers to afrequency at which the input impedance measured at said internal port ofthe radiating structure, when disconnected from the radiofrequencysystem, has an imaginary part equal to zero.

With the/each radiation booster being so small, and with the radiatingstructure including said radiation booster or boosters operating in afrequency range much lower than the first resonance frequency atthe/each internal port associated to the/each radiation booster, theinput impedance of the radiating structure (measured at the/eachinternal port when the radiofrequency system is disconnected) featuresan important reactive component (either capacitive or inductive) withinthe range of frequencies of the first and/or second frequency region ofoperation. That is, the input impedance of the radiating structure atthe/each internal port when disconnected from the radiofrequency systemhas an imaginary part not equal to zero for any frequency of the firstand/or second frequency region.

In some examples, the first resonance frequency at an internal port isat the same time located below (i.e., at a frequency lower than) thesecond frequency region of operation of the radiating system. Hence, thefirst resonance frequency at said internal port is located above thefirst frequency region but below the second frequency region.

In some cases, the first resonance frequency at the/each internal portof the radiating structure is also above the second frequency region ofoperation of the radiating system.

In some further examples, the first resonance frequency at an internalport of the radiating structure is located above a third frequencyregion of operation of the radiating system, said third frequency regionhaving a lowest frequency higher than the highest frequency of thesecond frequency region of operation of said radiating system.

In some examples the at least one radiation booster is substantiallyplanar defining a two-dimensional structure, while in other cases the atleast one radiation booster is a three-dimensional structure thatoccupies a volume. In particular, in some examples, the smallestdimension of a booster box is not smaller than a 70%, an 80% or even a90% of the largest dimension of said booster box, defining a volumetricgeometry. Radiation boosters having a volumetric geometric may beadvantageous to enhance the radioelectric performance of the radiatingstructure, particularly in those cases in which the maximum size of theradiation booster is very small relative to the free-space wavelengthcorresponding to the lowest frequency of the first and/or secondfrequency region.

Moreover, providing a radiation booster with a volumetric geometry canbe advantageous to reduce the other two dimensions of its radiator box,leading to a very compact solution. Therefore, in some examples in whichthe at least one radiation booster has a volumetric geometry, it ispreferred to set a ratio between the first resonance frequencyassociated to the/each internal port of the radiating structure whendisconnected from the radiofrequency system and the highest frequency ofthe first frequency region above 4.8, or even above 5.4.

In some advantageous examples, the radiating structure includes a firstradiation booster having a volumetric geometry and a second radiationbooster being substantially planar. In such examples, said firstradiation booster may preferably excite a radiation mode on the groundplane layer responsible for the operation of the radiating system in thefirst frequency region.

In a preferred embodiment, the at least one radiation booster comprisesa conductive part. In some cases said conductive part may take the formof, for instance but not limited to, a conducting strip comprising oneor more segments, a polygonal shape (including for instance triangles,squares, rectangles, hexagons, or even circles or ellipses as limitcases of polygons with a large number of edges), a polyhedral shapecomprising a plurality of faces (including also cylinders or spheres aslimit cases of polyhedrons with a large number of faces), or acombination thereof.

In some examples, the connection point of the at least one radiationbooster is advantageously located substantially close to an end, or to acorner, of said conductive part.

In another preferred example, the at least one radiation boostercomprises a gap (i.e., absence of conducting material) defined in theground plane layer. Said gap is delimited by one or more segmentsdefining a curve. The connection point of the radiation booster islocated at a first point along said curve. The connection point of theground plane layer is located at a second point along said curve, saidsecond point being different from said first point.

In yet another preferred example, a radiating structure includes a firstradiation booster comprising a conductive part and a second radiationbooster comprising a gap defined in the ground plane layer. Such anembodiment may be particularly advantageous in some cases to exciteradiation modes on the ground plane layer having substantiallyorthogonal polarizations, or an increased level of isolation.

In a preferred example of the present invention, a major portion of theat least one radiation booster (such as at least a 50%, or a 60%, or a70%, or an 80% of the surface of said radiation booster) is placed onone or more planes substantially parallel to the ground plane layer. Inthe context of this document, two surfaces are considered to besubstantially parallel if the smallest angle between a first line normalto one of the two surfaces and a second line normal to the other of thetwo surfaces is not larger than 30°, and preferably not larger than 20°,or even more preferably not larger than 10°.

In some examples, said one or more planes substantially parallel to theground plane layer and containing a major portion of a radiation boosterof the radiating structure are preferably at a height with respect tosaid ground plane layer not larger than a 2% of the free-spacewavelength corresponding to the lowest frequency of the first frequencyregion of operation of the radiating system. In some cases, said heightis smaller than 7 mm, preferably smaller than 5 mm, and more preferablysmaller than 3 mm.

In some embodiments, the at least one radiation booster is substantiallycoplanar to the ground plane layer. Furthermore, in some cases the atleast one radiation booster is advantageously embedded in the same PCBas the one containing the ground plane layer, which results in aradiating structure having a very low profile.

In some cases at least two, three, four, or even all, radiation boostersare substantially coplanar to each other, and preferably alsosubstantially coplanar to the ground plane layer.

In some cases, two or more radiation boosters may be arranged one on topof another forming for example a stacked configuration. In other cases,at least one radiation booster is arranged or embedded within anotherradiation booster (i.e., the booster box of said at least one radiationbooster is at least partially contained within the booster box of saidanother radiation booster). In such cases, even more compact solutionscan be obtained.

In a preferred example the radiating structure is arranged within thewireless handheld or portable device in such a manner that there is noground plane in the orthogonal projection of a radiation booster ontothe plane containing the ground plane layer. In some examples there issome overlapping between the projection of a radiation booster and theground plane layer. In some embodiments less than a 10%, a 20%, a 30%, a40%, a 50%, a 60% or even a 70% of the area of the projection of aradiation booster overlaps the ground plane layer. Yet in some otherexamples, the projection of a radiation booster onto the ground planelayer completely overlaps the ground plane layer.

In some cases it is advantageous to protrude at least a portion of theorthogonal projection of a radiation booster beyond the ground planelayer, or alternatively remove ground plane from at least a portion ofthe projection of a radiation booster, in order to adjust the levels ofimpedance and to enhance the impedance bandwidth of the radiatingstructure. This aspect is particularly suitable for those examples whenthe volume for the integration of the radiating structure has a smallheight, as it is the case in particular for slim wireless handheld orportable devices.

In some examples, at least one, two, three, or even all, radiationboosters are preferably located substantially close to an edge of theground plane layer, preferably said edge being in common with a side ofthe ground plane rectangle. In some examples, at least one radiationbooster is more preferably located substantially close to an end of saidedge or to the middle point of said edge.

In some embodiments said edge is preferably an edge of a substantiallyrectangular or elongated ground plane layer.

In an example, a radiation booster is located preferably substantiallyclose to a short side of the ground plane rectangle, and more preferablysubstantially close to an end of said short side or to the middle pointof said short side. Such a placement for a radiation booster withrespect to the ground plane layer is particularly advantageous when theradiating structure features at the internal port associated to saidradiation booster, when the radiofrequency system is disconnected, aninput impedance having a capacitive component for the frequencies of thefirst and second frequency regions of operation.

In another example, a radiation booster is located preferablysubstantially close to a long side of the ground plane rectangle, andmore preferably substantially close to an end of said long side or tothe middle point of said long side. Such a placement for a radiationbooster is particularly advantageous when the radiating structurefeatures at the internal port associated to said radiation booster, whenthe radiofrequency system is disconnected, an input impedance having aninductive component for the frequencies of said first and secondfrequency regions.

In some other examples, at least one radiation booster is advantageouslylocated substantially close to a corner of the ground plane layer,preferably said corner being in common with a corner of the ground planerectangle.

In the context of this document, two points are substantially close toeach other if the distance between them is less than 5% (more preferablyless than 3%, 2%, 1% or 0.5%) of the free-space wavelength correspondingto the lowest frequency of operation of the radiating system. In thesame way, two linear dimensions are substantially close to each other ifthey differ in less than 5% (more preferably less than 3%, 2%, 1% or0.5%) of said free-space wavelength.

In some examples, a radiating structure for a radiating system of awireless handheld or portable device comprises a first radiationbooster, a second radiation booster and a ground plane layer. Theradiating structure therefore comprises two internal ports: a firstinternal port being defined between a connection point of the firstradiation booster and the at least one connection point of the groundplane layer; and a second internal port being defined between aconnection point of the second radiation booster arid said at least oneconnection point of the ground plane layer.

In an advantageous example, the first radiation booster is substantiallyclose to a first corner of the ground plane layer and the secondradiation booster is substantially close to a second corner of theground plane layer (said second corner not being the same as said firstcorner). The first and second corners are preferably in common with twocorners of the ground plane rectangle associated to said ground planelayer and, more preferably, said two corners are at opposite ends of ashort side of the ground plane rectangle. Such a placement of theradiation boosters may be particularly interesting when it is necessaryto achieve higher isolation between the two internal ports of theradiating structure.

In another advantageous example, and in order to facilitate theinterconnection of the radiation boosters to the radiofrequency system,said first and second radiation booster are substantially close to afirst corner of the ground plane layer, the first corner beingpreferably in common with a corner of the ground plane rectangle. Inthis example, preferably, the first and the second radiation boostersare such that the first internal port, when the radiofrequency system isdisconnected, features an input impedance having an inductive componentfor .the frequencies of the first and second frequency regions, and thesecond internal port, also when the radiofrequency system isdisconnected, features an input impedance having a capacitive componentfor the frequencies of the first and second frequency regions.

In yet another advantageous embodiment, the first radiation booster islocated substantially close to a short edge of the ground plane layerand the second radiation booster is located substantially close to along edge of the ground plane layer. Preferably, said short edge andsaid long edge are in common with a short side and a long siderespectively of the ground plane rectangle and meet at a corner. Such achoice of the placement of the first and second radiation boosters maybe particularly advantageous to excite radiation modes on the groundplane layer having substantially orthogonal polarizations and/or toachieve an increased level of isolation between the two internal portsof the radiating structure.

In some examples, the at least one connection point of the ground planelayer is located advantageously close to the connection point of one ofthe at least one radiation boosters in order to facilitate theinterconnection of the radiofrequency system with the radiatingstructure. Therefore, those locations specified above as being preferredfor the placement of a radiation booster are also advantageous for thelocation of the at least one connection point of the ground plane layer.

Therefore, in some examples said at least one connection point islocated substantially close to an edge of the ground plane layer,preferably an edge in common with a side of the ground plane rectangle,or substantially close to a corner of the ground plane layer, preferablysaid corner being in common with a corner of the ground plane rectangle.Such an election of the position of the at least one connection point ofthe ground plane layer may be advantageous to provide a longer path tothe electrical currents flowing on the ground plane layer, lowering thefrequency of one or more radiation modes of the ground plane layer.

In some embodiments, the radiofrequency system comprises at least onematching network (such as for instance, one, two, three, four or morematching networks) to transform the input impedance of the radiatingstructure, providing impedance matching to the radiating system in atleast the first and second frequency regions of operation of theradiating system.

In a preferred example, the radiofrequency system comprises as manymatching networks as there are radiation boosters (and, consequently,internal ports) in the radiating structure.

In another preferred example, the radiofrequency system comprises asmany matching networks as there are frequency regions of operation ofthe radiating system. That is, in a radiating system operating forexample in a first and in a second frequency region, its radiofrequencysystem may advantageously comprise a first matching network to provideimpedance matching to the radiating system in said first frequencyregion and a second matching network to provide impedance matching tothe radiating system in said second frequency region.

The/each matching network can comprise a single stage or a plurality ofstages. In some examples, the/each matching network comprises at leasttwo, at least three, at least four, at least five, at least six, atleast seven, at least eight or more stages.

A stage comprises one or more circuit components (such as for examplebut not limited to inductors, capacitors, resistors, jumpers,short-circuits, switches, delay lines, resonators, or other reactive orresistive components). In some cases, a stage has a substantiallyinductive behavior in the frequency regions of operation of theradiating system, while another stage has a substantially capacitivebehavior in said frequency regions, and yet a third one may have asubstantially resistive behavior in said frequency regions.

A stage can be connected in series or in parallel to other stages and/orto one of the at least one port of the radiofrequency system.

In some examples, the at least one matching network alternates stagesconnected in series (i.e., cascaded) with stages connected in parallel(i.e., shunted), forming a ladder structure. In some cases, a matchingnetwork comprising two stages forms an L-shaped structure (i.e.,series—parallel or parallel—series). In some other cases, a matchingnetwork comprising three stages forms either a pi-shaped structure(i.e., parallel—series—parallel) or a T-shaped structure (i.e.,series—parallel—series).

In some examples, the at least one matching network alternates stageshaving a substantially inductive behavior, with stages having asubstantially capacitive behavior.

In an example, a stage may substantially behave as a resonant circuit(such as, for instance, a parallel LC resonant circuit or a series LCresonant circuit) in at least one frequency region of operation of theradiating system (such as for instance in the first or the secondfrequency region). The use of stages having a resonant circuit behaviorallows one part of a given matching network be effectively connected toanother part of said matching network for a given range of frequencies,or in a given frequency region, and be effectively disabled for anotherrange of frequencies, or in another frequency region.

In an example, the at least one matching network comprises at least oneactive circuit component (such as for instance, but not limited to, atransistor, a diode, a MEMS device, a relay, or an amplifier) in atleast one stage.

In some embodiments, the/each matching network preferably includes areactance cancellation circuit comprising one or more stages, with oneof said one or more stages being connected to a port of theradiofrequency system, said port being for interconnection with aninternal port of the radiating structure.

In the context of this document, reactance cancellation preferablyrefers to compensating the imaginary part of the input impedance at aninternal port of the radiating structure when disconnected from theradiofrequency system so that the input impedance of the radiatingsystem at an external port has an imaginary part substantially close tozero for a frequency preferably within a frequency region of operation(such as for instance, the first or the second frequency regions). Insome less preferred examples, said frequency may also be higher than thehighest frequency of said frequency region (although preferably nothigher than 1.1, 1.2, 1.3 or 1.4 times said highest frequency) or lowerthan the lowest frequency of said frequency region (although preferablynot lower than 0.9, 0.8 or 0.7 times said lowest frequency). Moreover,the imaginary part of an impedance is considered to be substantiallyclose to zero if it is not larger (in absolute value) than 15 Ohms, andpreferably not larger than 10 Ohms, and more preferably not larger than5 Ohms.

In a preferred embodiment, the radiating structure features at a firstinternal port when the radiofrequency system is disconnected from saidfirst internal port an input impedance having a capacitive component forthe frequencies of the first and second frequency regions of operation.In that embodiment, a matching network interconnected to said firstinternal port (via a port of the radiofrequency system) includes areactance cancellation circuit that comprises a first stage having asubstantially inductive behavior for all the frequencies of the firstand second frequency regions of operation of the radiating system. Morepreferably, said first stage comprises an inductor. In some cases, saidinductor may be a lumped inductor. Said first stage is advantageouslyconnected in series with said port of the radiofrequency system that isinterconnected to said first internal port of the radiating structure ofa radiating system.

In another preferred embodiment, the radiating structure features at afirst internal port when the radiofrequency system is disconnected fromsaid first internal port an input impedance having an inductivecomponent for the frequencies of the first and second frequency regionsof operation. In that embodiment, a matching network interconnected tosaid first internal port (via a port of the radiofrequency system)includes a reactance cancellation circuit that comprises a first stageand a second stage forming an L-shaped structure, with said first stagebeing connected in parallel and said second stage being connected inseries. Each of the first and the second stage has a substantiallycapacitive behavior for all the frequencies of the first and secondfrequency regions of operation of the radiating system. More preferably,said first stage and said second stage comprise each a capacitor. Insome cases, said capacitor may be a lumped capacitor. Said first stageis advantageously connected in parallel with said port of theradiofrequency system that is interconnected to said first internal portof the radiating structure of a radiating system, while said secondstage is connected to said first stage.

In yet another preferred embodiment, the radiating structure comprises afirst internal port that features, when said first internal port isdisconnected from the radiofrequency system, an input impedance having—acapacitive component for the frequencies of the first and secondfrequency regions of operation and a second internal port that features(also when said second internal port is disconnected from theradiofrequency system) an input impedance having an inductive componentfor the frequencies of the first and second frequency regions ofoperation.

In some embodiments, the at least one matching network may furthercomprise a broadband matching circuit, said broadband matching circuitbeing preferably connected in cascade to the reactance cancellationcircuit. With a broadband matching circuit, the impedance bandwidth ofthe radiating structure may be advantageously increased. This may beparticularly interesting for those cases in which the relative bandwidthof the first and/or second frequency region is large.

In a preferred embodiment, the broadband matching circuit comprises astage that substantially behaves as a resonant circuit (preferably as aparallel LC resonant circuit or as a series LC resonant circuit) in oneof the at least two frequency regions of operation of the radiatingsystem.

In some examples, the at least one matching network may further comprisein addition to the reactance cancellation circuit and/or the broadbandmatching circuit, a fine tuning circuit to correct small deviations ofthe input impedance of the radiating system with respect to some giventarget specifications.

In a preferred example, a matching network comprises: a reactancecancellation circuit connected to a first port of the radiofrequencysystem, said first port being connected to an internal port of theradiating structure; and a fine tuning circuit connected to a secondport of the radiofrequency system, said second port being connected toan external port of the radiating system. In an example, said matchingnetwork further comprises a broadband matching circuit operationallyconnected in cascade between the reactance cancellation circuit and thefine tuning circuit. In another example, said matching network does notcomprise a broadband matching circuit and the reactance cancellationcircuit is connected in cascade directly to the fine tuning circuit.

In some examples, at least some circuit components in the stages of theat least ne matching network are discrete lumped components (such as forinstance SMT components), while in some other examples all the circuitcomponents of the at least one matching network are discrete lumpedcomponents. In some examples, at least some circuit components in thestages of the at least one matching network are distributed components(such as for instance a transmission line printed or embedded in a PCBcontaining the ground plane layer of the radiating structure), while insome other examples all the circuit components of the at least onematching network are distributed components.

In some examples, at least some, or even all, circuit components in thestages of the at least one matching network may be integrated into anintegrated circuit, such as for instance a CMOS integrated circuit or ahybrid integrated circuit.

In some embodiments, the radiofrequency system may comprise a frequencyselective element such as a diplexer or a bank of filters to separate,or to combine, the electrical signals of the different frequency regionsof operation of the radiating system.

In an example, the radiofrequency system comprises a first diplexer toseparate the electrical signals of the first and second frequencyregions of operation of the radiating system, a first matching networkto provide impedance matching in said first frequency region, a secondmatching network to provide impedance matching in said second frequencyregion, and a second diplexer to recombine the electrical signals ofsaid first and second frequency regions.

Alternatively, a diplexer can be replaced by a bank of band-pass filtersand a combiner/splitter. Also, a diplexer and a bank of band-passfilters may be used in the radiofrequency system. Preferably, there areas many band-pass filters in the bank of band-pass filters as there arefrequency regions of operation of the radiating system. Each one of theband-pass filters is designed to introduce low insertion loss in adifferent frequency region and to present high impedance to thecombiner/splitter in the other frequency regions. The combiner/splittercombines (or splits) the electrical signals of the different frequencyregions of operation of the radiating system.

In the context of this document high impedance in a given frequencyregion preferably refers to impedance having a modulus not smaller than150 Ohms, 200 Ohms, 300 Ohms, 500 Ohms or even 1000 Ohms for anyfrequency within said frequency region, and more preferably beingsubstantially reactive (i.e., having a real part substantially close tozero) within said given frequency region.

In some examples, one, two, three or even all the stages of the at leastone matching network may contribute to more than one functionality ofsaid at least one matching network. A given stage may for instancecontribute to two or more of the following functionalities from thegroup comprising: reactance cancellation, impedance transformation(preferably, transformation of the real part of said impedance),broadband matching and fine tuning matching. In other words, a samestage of the at least one matching network may advantageously belong totwo or three of the following circuits: reactance cancellation circuit,broadband matching circuit and fine tuning circuit. Using a same stageof the at least one matching network for several purposes may beadvantageous in reducing the number of stages and/or circuit componentsrequired for the at least one matching network of a radiofrequencysystem, reducing the real estate requirements on the PCB of theantennaless wireless handheld or portable device in which the radiatingsystem is integrated.

In other examples, each stage of the at least one matching networkserves only to one functionality within the matching network. Such achoice may be preferred when low-end circuit components, having forinstance a worse tolerance behavior, a more pronounced thermaldependence, and/or a lower quality factor, are used to implement said atleast one matching network.

In some embodiments one, two, three or more radiation boosters may beadvantageously arranged in an integrated circuit package (i.e., apackage having a form factor for integrated circuit packages). Saidintegrated circuit package may advantageously comprise a semiconductorchip or die arranged inside the package. Moreover, said radiationbooster or boosters is/are preferably arranged in the package but not insaid semiconductor die or chip. In some of these examples, theintegrated circuit package may also include at least part of, or evenall, the radiofrequency system.

BRIEF DESCRIPTION OF THE DRAWINGS

Embodiments of the invention are shown in the enclosed figures. Hereinshows:

FIG. 1(a)—Example of an antennaless wireless handheld or portable deviceincluding a radiating system according to the present invention; andFIG. 1(b)—Block diagram of an antennaless wireless handheld or portabledevice illustrating the basic functional blocks thereof.

FIGS. 2(a)-2(c)—Schematic representations of three examples of radiatingsystems according to the present invention.

FIGS. 3(a)-3(c)—Block diagrams of three examples of matching networksfor a radiofrequency system used in a radiating system according to thepresent invention.

FIGS. 4(a) and 4(b)—Example of a radiating structure for a radiatingsystem, the radiating structure including a first and a second radiationbooster, each comprising a conductive part: FIG. 4(a)—Partialperspective view; and FIG. 4(b)—top plan view.

FIG. 5—Schematic representation of a radiofrequency system for aradiating system whose radiating structure is shown in FIGS. 4(a) and4(b).

FIGS. 6(a)—Schematic representation of a matching network used in theradiofrequency system of FIG. 5; and FIG. 6(b)—Schematic representationof a first and a second band-pass filter and a combiner/splitter used inthe radiofrequency system of FIG. 5.

FIGS. 7(a)-7(c)—Typical impedance transformation caused by the matchingnetwork of FIGS. 6(a) and 6(b) on the input impedance at the firstinternal port of the radiating structure of FIGS. 4(a) and 4(b): FIG.7(a)—Input impedance at the first internal port when disconnected fromthe matching network of the radiofrequency system; FIG. 7(b)—Inputimpedance after connection of a reactance cancellation circuit to thefirst internal port; and FIG. 7(c)—Input impedance after connection of abroadband matching circuit in cascade with the reactance cancellationcircuit.

FIGS. 8(a)-8(c)—Typical impedance transformation caused by a matchingnetwork similar to that of FIGS. 6(a) and 6(b) on the input impedance atthe second internal port of the radiating structure of FIGS. 4(a) and4(b): FIG. 8(a)—Input impedance at the second internal port whendisconnected from the matching network of the radiofrequency system;FIG. 8(b)—Input impedance after connection of a reactance cancellationcircuit to the second internal port; and FIG. 8(c)—Input impedance afterconnection of a broadband matching circuit in cascade with saidreactance cancellation circuit.

FIG. 9(a)—Typical input return losses at the first internal port of theradiating structure of FIGS. 4(a) and 4(b) compared with those afterinterconnection of the matching network of FIGS. 6(a) and 6(b) to thefirst internal port of the radiating structure; and FIG. 9(b)—Typicalinput return losses at the second internal port of the radiatingstructure of FIGS. 4(a) and 4(b) compared with those afterinterconnection of a matching network similar to that of FIGS. 6(a) and6(b) to the second internal port of the radiating structure.

FIG. 10—Typical input return losses at the external port of theradiating system resulting from the interconnection of the radiatingsystem of FIG. 5 to the radiating structure of FIGS. 4(a) and 4(b).

FIGS. 11(a) and 11(b)—Partial perspective views of first and secondexamples, respectively, of radiating structures comprising two radiationboosters according to the present invention.

FIG. 12—Partial perspective view of another example of a radiatingstructure comprising two radiation boosters.

FIG. 13—Partial perspective view of a radiating structure comprising tworadiation boosters arranged one on top of another in a stackedconfiguration.

FIGS. 14(a)-14(c)—Partial perspective views of first, second and thirdexamples, respectively, of radiating structures for a radiating system,each radiating structure including a first radiation booster comprisinga conductive part and a second radiation booster comprising a gapdefined in a ground plane layer.

FIG. 15—Example of a radiating structure for a radiating systemaccording to the present invention, the radiating structure includingonly one radiation booster.

FIG. 16—Schematic representation of a radiofrequency system for aradiating system whose radiating structure is shown in FIG. 15.

FIG. 17—Radiating structure of a typical wireless handheld or portabledevice.

FIG. 18—Partial top plan view of a partially-populated PCB showing thelayout of the ground plane layer of a radiating structure and theconducting traces and pads of a radiofrequency system.

DETAILED DESCRIPTION

Further characteristics and advantages of the invention will becomeapparent in view of the detailed description of some preferredembodiments which follows. Said detailed description of some preferredembodiments of the invention is given for purposes of illustration onlyand in no way is meant as a definition of the limits of the invention,made with reference to the accompanying figures.

FIG. 1 shows an illustrative example of an antennaless wireless handheldor portable device 100 capable of multiband operation according to thepresent invention. In FIG. 1 a, there is shown an exploded perspectiveview of the antennaless wireless handheld or portable device 100comprising a radiating structure that includes a first radiation booster15 a, a second radiation booster 151 b and a ground plane layer 152(which could be included in a layer of a multilayer PCB). Theantennaless wireless handheld or portable device 100 also comprises aradiofrequency system 153, which is interconnected with said radiatingstructure.

Referring now to FIG. 1 b, it is shown a block diagram of theantennaless wireless handheld or portable device 100 capable ofmultiband operation advantageously comprising, in accordance to thepresent invention, a user interface module 101, a processing module 102,a memory module 103, a communication module 104 and a power managementmodule 105. In a preferred embodiment, the processing module 102 and thememory module 103 have herein been listed as separate modules. However,in another embodiment, the processing module 102 and the memory module103 may be separate functionalities within a single module or aplurality of modules. In a further embodiment, two or more of the fivefunctional blocks of the antennaless wireless handheld or portabledevice 100 may be separate functionalities within a single module or aplurality of modules.

In FIG. 2, it is shown a schematic representation of three examples ofradiating systems for an antennaless wireless handheld or portabledevice capable of multiband operation according to the presentinvention.

In particular, in FIG. 2a a radiating system 200 comprises a radiatingstructure 201, a radiofrequency system 202, and an external port 203.The radiating structure 201 comprises a radiation booster 204, whichincludes a connection point 205, and a ground plane layer 206, saidground plane layer also including a connection point 207. The radiatingstructure 201 further comprises an internal port 208 defined between theconnection point of the radiation booster 205 and the connection pointof the ground plane layer 207. Furthermore, the radiofrequency system202 comprises two ports: a first port 209 is connected to the internalport of the radiating structure 208, and a second port 210 is connectedto the external port of the radiating system 203.

Referring now to FIG. 2b , a radiating system 230 comprises a radiatingstructure 231, which, in addition to a first radiation booster 204 and aground plane layer 206, also includes a second radiation booster 234.The radiating structure 231 comprises two internal ports: A firstinternal port 208 is defined between a connection point of the firstradiation booster 205 and a connection point of the ground plane layer207; while a second internal port 238 is defined between a connectionpoint of the second radiation booster 235 and the same connection pointof the ground plane layer 207.

The radiating system 230 comprises a radiofrequency system 232 includingthree ports: A first port 209 is connected to the first internal port208; a second port 239 is connected to the second internal port 238; anda third port 210 is connected to the external port of the radiatingsystem 203. That is, the radiofrequency system 232 comprises a portconnected to each of the at least one internal ports of the radiatingstructure 231, and a port connected to the external port of theradiating system 203.

FIG. 2c depicts a further example of a radiating system 260 having thesame radiating structure 201 as in the example of FIG. 2a . However,differently from the example of FIG. 2a , the radiating system 260comprises an additional external port 263.

The radiating system 260 includes a radiofrequency system 262 having afirst port 209 connected to the internal port of the radiating structure208, a second port 210 connected to the external port 203, and a thirdport 270 connected to the additional external port 263.

Such a radiating system 260 may be preferred when said radiating system260 is to provide operation in at least one cellular communicationstandard and at least one wireless connectivity standard. In oneexample, the external port 203 may provide the GSM 900 and GSM 1800standards, while the external port 263 may provide an IEEE802.11standard.

FIG. 3 shows the block diagram of three preferred examples of a matchingnetwork 300 for a radiofrequency system, the matching network 300comprising a first port 301 and a second port 302. One of said two portsmay at the same time be a port of a radiofrequency system and, inparticular, be interconnected with an internal port of a radiatingstructure.

In FIG. 3a the matching network 300 comprises a reactance cancellationcircuit 303. In this example, a first port of the reactance cancellationcircuit 304 may be operationally connected to the first port of thematching network 301 and another port of the reactance cancellationcircuit 305 may be operationally connected to the second port of thematching network 302.

Referring now to FIG. 3b , the matching network 300 comprises thereactance cancellation circuit 303 and a broadband matching circuit 330,which is advantageously connected in cascade with the reactancecancellation circuit 303. That is, a port of the broadband matchingcircuit 331 is connected to port 305. In this example, port 304 isoperationally connected to the first port of the matching network 301,while another port of the broadband matching circuit 332 isoperationally connected to the second port of the matching network 302.

FIG. 3c depicts a further example of the matching network 300comprising, in addition to the reactance cancellation circuit 303 andthe broadband matching circuit 330, a fine tuning circuit 360. Saidthree circuits are advantageously connected in cascade, with a port ofthe reactance cancellation circuit (in particular port 304) beingconnected to the first port of the matching network 301 and a port thefine tuning circuit 362 being connected to the second port of thematching network 302. In this example, the broadband matching circuit330 is operationally interconnected between the reactance cancellationcircuit 303 and the fine tuning circuit 360 (i.e., port 331 is connectedto port 305 and port 332 is connected to port 361 of the fine tuningcircuit 360).

The radiofrequency systems 202, 232, 262 in the example radiatingsystems of FIG. 2 may advantageously include at least one, andpreferably two, matching networks such as the matching network 300 ofFIGS. 3a -c.

FIG. 4 shows a preferred example of a radiating structure suitable for aradiating system operating in a first frequency region of theelectromagnetic spectrum between 824 MHz and 960 MHz and in a secondfrequency region of the electromagnetic spectrum between 1710 MHz and2170 MHz. An antennaless wireless handheld or portable device includingsuch a radiating system may advantageously operate the GSM 850, GSM 900,GSM1800, GSM1900 and UMTS cellular communication standards (i.e., fivedifferent communication standards).

The radiating structure 400 comprises a first radiation booster 401, asecond radiation booster 405, and a ground plane layer 402. In FIG. 4b ,there is shown in a top plan view the ground plane rectangle 450associated to the ground plane layer 402. In this example, since theground plane layer 402 has a substantially rectangular shape, its groundplane rectangle 450 is readily obtained as the rectangular perimeter ofsaid ground plane layer 402.

The ground plane rectangle 450 has a long side of approximately 100 mmand a short side of approximately 40 mm. Therefore, in accordance withan aspect of the present invention, the ratio between the long side ofthe ground plane rectangle 450 and the free-space wavelengthcorresponding to” the lowest frequency of the first frequency region(i.e., 824 MHz) is advantageously larger than 0.2. Moreover, said ratiois advantageously also smaller than 1.0.

In this example, the first radiation booster 401 and the secondradiation booster 405 are of the same type, shape and size. However, inother examples the radiation boosters 401, 405 could be of differenttypes, shapes and/or sizes. Thus, in FIG. 4 each of the first and thesecond radiation boosters 401, 405 includes a conductive part featuringa polyhedral shape comprising six faces. Moreover, in this case said sixfaces are substantially square having an edge length of approximately 5mm, which means that said conductive part is a cube.

In this case, the conductive part of each of the two radiation boosters401, 405 is not connected to the ground plane layer 402. A first boosterbox 451 for the first radiation booster 401 coincides with the externalarea of said first radiation booster 401. Similarly, a second boosterbox 452 for the second radiation booster 405 coincides with the externalarea of said second radiation booster 405. In FIG. 4b , it is shown atop plan view of the radiating structure 400, in which the top face ofthe first booster box 451 and that of the second booster b9x 452 can beobserved.

In accordance with an aspect of the present invention, a maximum size ofthe first radiation booster 401 (said maximum size being a largest edgeof the first booster box 451) is advantageously smaller than 1/50 timesthe free-space wavelength corresponding to the lowest frequency of thefirst frequency region of operation of the radiating structure 400, anda maximum size of the second radiation booster 405 (said maximum sizebeing a largest edge of the second booster box 452) is alsoadvantageously smaller than 1/50 times said free-space wavelength. Inparticular, said maximum sizes of the first and second radiationboosters 401, 405 are also advantageously larger than 1/180 times saidfree-space wavelength.

Furthermore in this example, the first and second radiation boostershave each a maximum size smaller than 1/30 times the free-spacewavelength corresponding to the lowest frequency of the second frequencyregion of operation of the radiating structure 400, but advantageouslylarger than 1/120 times said free-space wavelength.

In FIG. 4, the first and second radiation boosters 401, 405 are arrangedwith respect to the ground plane layer 402 so that the upper and bottomfaces of the first radiation booster 401 and the upper and bottom facesof the second radiation booster 405 are substantially parallel to theground plane layer 402. Moreover, the bottom face of the first radiationbooster 401 is advantageously coplanar to the bottom face of the secondradiation booster 405, and the bottom faces of both radiation boosters401, 405 are also advantageously coplanar to the ground plane layer 402.With such an arrangement, the height of the radiation boosters 401, 405with respect to the ground plane layer is not larger than 2% of thefree-space wavelength corresponding to the lowest frequency of the firstfrequency region.

In the radiating structure 400, the first radiation booster 401 and thesecond radiation booster 405 protrude beyond the ground plane layer 402.That is, the radiation boosters 401, 405 are arranged with respect tothe ground plane layer 402 in such a manner that there is no groundplane in the orthogonal projection of the radiation boosters 401, 405onto the plane containing the ground plane layer 402. The firstradiation booster 401 is located substantially close to a first cornerof the ground plane layer 402, while the second radiation booster 405 islocated substantially close to a second corner of said ground planelayer 402. In particular, said first and second corners are at oppositeends of a short edge of the substantially rectangular ground plane layer402.

The first radiation booster 401 comprises a connection point 403 locatedon the lower right corner of the bottom face of the first radiationbooster 401. In turn, the ground plane layer 402 also comprises a firstconnection point 404 substantially on the upper right corner of theground plane layer 402. A first internal port of the radiating structure400 is defined between said connection point 403 and said firstconnection point 404.

Similarly, the second radiation booster 405 comprises a connection point406 located on the lower left corner of the bottom face of the secondradiation booster 405, and the ground plane layer 402 also comprises asecond connection point 407 substantially on the upper left corner ofthe ground plane layer 402. A second internal port of the radiatingstructure 400 is defined between said connection point 406 and saidsecond connection point 407.

In an alternative example, the ground plane layer 402 of the radiatingstructure 400 may comprise only the first connection point 404 (i.e.,only one connection point). In that case the second internal port couldhave been defined between the connection point 406 of the secondradiation booster 405 and said first connection point 404.

The very small dimensions of the first and second radiation boosters401, 405 result in said radiating structure 400 having at each of thefirst and second internal ports a first resonance frequency at afrequency much higher than the frequencies of the first frequencyregion. In this case, the ratio between the first resonance frequency ofthe radiating structure 400 measured at each of the first and secondinternal ports (in absence of a radiofrequency system connected to them)and the highest frequency of the first frequency region isadvantageously larger than 4.2.

Furthermore, the first resonance frequency at each of .the first andsecond internal ports of the radiating structure 400 is also at afrequency much higher than the frequencies of the second frequencyregion.

With such small dimensions of the first and second radiation boosters401, 405, the input impedance of the radiating structure 400 measured ateach of the first and second internal ports features an importantreactive component, and in particular a capacitive component, within thefrequencies of the first and second frequency regions, as it can beobserved in FIGS. 7a and 8 a.

In FIG. 7a , curve 700 represents on a Smith chart the typical compleximpedance at the first internal port of the radiating structure 400 as afunction of the frequency when no radiofrequency system is connected tosaid first internal port. In particular, point 701 corresponds to theinput impedance at the lowest frequency of the first frequency region,and point 702 corresponds to the input impedance at the highestfrequency of the first frequency region.

Curve 700 is located on the lower half of the Smith chart, which indeedindicates that the input impedance at the first internal port has acapacitive component (i.e., the imaginary part of the input impedancehas a negative value) for at least all frequencies of the firstfrequency range (i.e., between point 701 and point 702). Although notrepresented in FIG. 7a , the input impedance at the first internal porthas also a capacitive component for all frequencies of the secondfrequency region (i.e., curve 700 remains in the lower half of the Smithchart for all frequencies of the second frequency region).

As far as the second internal port of the radiating structure 400 isconcerned, curve 800 in FIG. 8a represents the typical complex impedanceat said second internal port as a function of the frequency in absenceof any radiofrequency system connected to it. Point 801 corresponds tothe input impedance at the lowest frequency of the second frequencyregion, and point 802 corresponds to the input impedance at the highestfrequency of the second frequency region.

Curve 800 is also located on the lower half of the Smith chart,indicating that the input impedance at the second internal port has acapacitive component for at least all frequencies of the secondfrequency range (i.e., between point 801 and point 802). Moreover,despite not being shown in FIG. 8a , the input impedance at the secondinternal port has also a capacitive component for all frequencies of thefirst frequency region (i.e., curve 800 remains in the lower half of theSmith chart for all frequencies of the first frequency region).

FIG. 5 presents a schematic of a radiofrequency system 500 to beconnected to the two internal ports of the radiating structure 400 inorder to transform the input impedance of the radiating structure 400and provide impedance matching in the first and second regions ofoperation of the radiating system.

The radiofrequency system 500 comprises two ports 501, 502 to beconnected respectively to the first and second internal ports of theradiating structure 400, and a third port 503 to be connected to asingle external port of the radiating system.

The radiofrequency system 500 also comprises a first matching network504 connected to port 501, providing impedance matching within the firstfrequency region; and a second matching network 505 connected to port502, providing impedance matching within the second frequency region.

The radiofrequency system 500 further comprises a first band-pass filter506 connected to said first matching network 504, and a second band-passfilter 507 connected to said second matching network 505. The firstband-pass filter 506 is designed to present low insertion loss in thefirst frequency region and high impedance in the second frequency regionof operation of the radiating system.

Analogously, the second band-pass filter 507 is designed to present lowinsertion loss in said second frequency region and high impedance insaid first frequency region.

The radiofrequency system 500 additionally includes a combiner/splitter508 to combine (or split) the electrical signals of different frequencyregions. Said combiner/splitter 508 is connected to the first and secondband-pass filters 506, 507, and to the port 503.

FIG. 6b shows a schematic representation of the first and secondband-pass filters 506, 507 and the combiner/splitter 508.

The first and second band-pass filters 506, 507 comprise each at leasttwo stages, and preferably at least one of said at least two stagesincludes an LC resonant circuit. In the particular example shown in FIG.6b , the first and the second band-pass filter 506, 507 have each twostages in an L-shaped (i.e., parallel—series) arrangement. Furthermore,each of said two stages includes an LC-resonant circuit formed by aJumped capacitor in parallel with a lumped inductor.

In some examples, the combiner/splitter 508 can be advantageouslyconstructed by directly connecting in parallel the two band-pass filters506, 507 to the port 503, as it is shown in the example of FIG. 6b .This is possible because in the first frequency region the secondband-pass filter 507 does not load the port 503, while in the secondfrequency region the first band-pass filter 506 does not load the port503. In other words, it is as if only one of the two matching networkswere effectively connected to the port 503 in each frequency region.

FIG. 6a is a schematic representation of the matching network 504, whichcomprises a first port 601 to be connected to the first internal port ofthe radiating structure 400 (via the port 501 of the radiofrequencysystem 500), and a second port 602 to be connected to the firstband-pass filter 506 of the radiofrequency system 500. In this example,the matching network 504 further comprises a reactance cancellationcircuit 607 and a broadband matching circuit 608.

The reactance cancellation circuit 607 includes one stage comprising onesingle circuit component 604 arranged in series and featuring asubstantially inductive behavior in the first and second frequencyregions. In this particular example, the circuit component 604 is alumped inductor. The inductive behavior of the reactance cancellationcircuit 607 advantageously compensates the capacitive component of theinput impedance of the first internal port of the radiating structure400.

Such a reactance cancellation effect can be observed in FIG. 7b , inwhich the input impedance at the first internal port of the radiatingstructure 400 (curve 700 in FIG. 7a ) is transformed by the reactancecancellation circuit 607 into an impedance having an imaginary partsubstantially close to zero in the first frequency region (see FIG. 7b). Curve 730 in FIG. 7b corresponds to the input impedance that would beobserved at the second port 602 of the first matching network 504 (whendisconnected from the first band-pass filter 506) if the broadbandmatching circuit 608 were removed and said second port 602 were directlyconnected to a port 603. Said curve 730 crosses the horizontal axis ofthe Smith Chart at a point 731 located between point 701 and point 702,which means that the input impedance at the first internal port of theradiating structure 400 has an imaginary part equal to zero for afrequency advantageously between the lowest and highest frequencies ofthe first frequency region.

The broadband matching circuit 608 includes also one stage and isconnected in cascade with the reactance cancellation circuit 607. Saidstage of the broadband matching circuit 608 comprises two circuitcomponents: a first circuit component 605 is a lumped inductor and asecond circuit component 606 is a lumped capacitor. Together, thecircuit components 605 and 606 form a parallel LC resonant circuit(i.e., said stage of the broadband matching circuit 608 behavessubstantially as a resonant circuit in the first frequency region ofoperation).

Comparing FIGS. 7b and 7c , it is noticed that the broadband matchingcircuit 608 has the beneficial effect of “closing in” the ends of curve730 (i.e., transforming the curve 730 into another curve 760 featuring acompact loop around the center of the Smith chart). Thus, the resultingcurve 760 exhibits an input impedance (now, measured at the second port602 when disconnected from the first band-pass filter 506) within avoltage standing wave ratio (VSWR) 3:1 referred to a reference impedanceof 50 Ohms over a broader range of frequencies.

In this particular example, the second matching network 505 of theradiofrequency system 500 has the same configuration as that of thefirst matching network 504 shown in FIG. 6a : A reactance cancellationcircuit that includes one stage comprising one single circuit componentarranged in series and featuring a substantially inductive behavior inthe first and second frequency regions; and a broadband matching circuitconnected in cascade with the reactance cancellation circuit and thatincludes also one stage, said stage comprising two circuit componentsthat form a parallel LC resonant circuit so that said stage behavessubstantially as a resonant circuit in the second frequency region ofoperation. Said second matching network also comprises a first port tobe connected to the second internal port of the radiating structure 400(via the port 502 of the radiofrequency system 500), and a second portto be connected to the second band-pass filter 507.

Despite the fact that the first and second matching networks 504, 505have the same configuration, the different frequency ranges in whicheach matching network is to provide impedance matching makes the actualvalues of the circuit components used in each matching network bepossibly different.

The effect of the reactance cancellation circuit of the second matchingnetwork 505 on the input impedance at the second internal port of theradiating structure 400 is shown in Figure Sb, in which the inputimpedance at said second internal port (curve 800 in Figure Sa) istransformed into an impedance having an imaginary part substantiallyclose to zero in the second frequency region. Curve 830 in FIG. 8bcorresponds to the input impedance that would be observed at the secondport of the second matching network 505 (when disconnected from thefirst band-pass filter 507) if said second matching network 505 had onlya reactance cancellation circuit operationally connected between itsfirst and second ports. Said curve 830 crosses the horizontal axis ofthe Smith Chart at a point 831 located between point 801 and point 802,which means that the input impedance at the second internal port of theradiating structure 400 has an imaginary part equal to zero for afrequency advantageously between the lowest and highest frequencies ofthe second frequency region.

Finally, the broadband matching circuit of the second matching network505 transforms the curve 830 in FIG. 8b into another curve 860 (in FIG.8c ) that features a compact loop around the center of the Smith chart.Thus, the resulting curve 860 exhibits an input impedance (now, measuredat the second port of the second matching network 505 when disconnectedfrom the second band-pass filter 507) within a VSWR 3:1 referred to areference impedance of 50 Ohms over a broader range of frequencies.

Alternatively, the effect of the first and second matching networks ofthe radiofrequency system of FIG. 5 on the radiating structure of FIG. 4can be compared in terms of the input return loss. In FIG. 9a curve 900(in dash-dotted line) presents the typical input return loss of theradiating structure 400 observed at its first internal port when theradiofrequency system 500 is not connected to said first internal port.From said curve 900 it is clear that the radiating structure 400 is notmatched in the first frequency region and that the first radiationbooster 401 is non-resonant in said first frequency region. On the otherhand, curve 910 (in solid line) corresponds to the input return lossesat the second port 602 of the first matching network 504 (whendisconnected fro the first band-pass filter 506).

Likewise, in FIG. 9b curve 950 (in dash-dotted line) presents thetypical input return loss of the radiating structure 400 observed at itssecond internal port when the radiofrequency system 500 is not connectedto said second internal port. From said curve 950 it is clear that theradiating structure 400 is not matched in the second frequency regionand that the second radiation booster 405 is non-resonant in said secondfrequency region. On the other hand, curve 960 (in solid line)corresponds to the input return losses at the second port of the secondmatching network 505 (when disconnected from the second band-pass filter507).

The first and second matching networks 504, 505 of the radiofrequencysystem 500 transform the input impedance of the first and secondinternal ports of the radiating structure 400 to provide impedancematching respectively in the first and second frequency regions. Indeed,curve 910 exhibits return losses better than −6 dB in the firstfrequency region (delimited by points 901 and 902 on the curve 910),while curve 960 exhibits return losses better than −6 dB in the secondfrequency region (delimited by points 951 and 952 on the curve 960).

Finally, the frequency response of the radiating system resulting fromthe interconnection of the radiating system of FIG. 5 to the radiatingstructure of FIG. 4 is shown in FIG. 10, in which the curve 1000corresponds to the return loss observed at the external port of theradiating system. The return loss curve 1000 exhibits a better than −6dB behavior in the first frequency region (delimited by points 1001 and1002 on said curve 1000) and in the second frequency region (delimitedby points 1003 and 1004), making it possible for the radiating system toprovide operability for the GSM850, GSM900, GSM1800, GSM1900 and UMTSstandards.

The radiating structure of FIG. 4 and the radiofrequency system of FIG.5 could be advantageously provided on a common layer of a PCB, as it isshown in FIG. 18, in which on a layer of a PCB 1800 it is provided aground plane layer 1802 and the conducting traces and pads of theradiofrequency system that make it possible to interconnect a first anda second radiation booster to an external port 1810, which is connectedto an integrated circuit chip 1804 performing radiofrequencyfunctionality .

The first radiation booster 401 in FIG. 4 could be mounted on a firstarea 1801 of the PCB 1800 (delimited with a dash-dotted line) and theconnection point 403 of the first radiation booster 401 be electricallyconnected (e.g., soldered) to a mounting pad 1803. Analogously, thesecond radiation booster 405 could be provided on a second area 1805(also delimited with a dash-dotted line on the PCB 1800), and theconnection point 406 of said second radiation booster 405 beelectrically connected to a mounting pad 1806.

A plurality of pads 1807 is provided in order to mount the circuitcomponents 1811, 1812 of the matching networks and band-pass filters ofthe radiofrequency system 500. The pads 1807 are laid out adjacent to anedge of the ground plane layer 1802 to facilitate mounting shuntedcircuit components 1812.

Furthermore, conducting traces 1808, 1809 allow routing the signalsbetween the mounting pads 1803, 1806 and the external port 1810. Inparticular, conducting trace 1808 together with the ground plane layer1802 defines a coplanar transmission line. In an example, saidtransmission line features a characteristic impedance of 50 Ohms. Inanother example, the conducting trace 1808 is designed so that saidtransmission line cooperates with a band-pass filter of theradiofrequency system to present high impedance to the external port1810.

Referring now to FIG. 11, it is shown a partial perspective view of twoexamples of radiating structures for a radiating system of a wirelesshandheld or portable device comprising two radiation boosters.

In particular, FIG. 11a presents a radiating structure 1100 comprising afirst radiation booster 1101, a second radiation booster 1105, and aground plane layer 1102. The radiating structure 1100 comprises twointernal ports: a first internal port being defined between a connectionpoint of the first radiation booster 1103 and a first connection pointof the ground plane layer 1104; and a second internal port being definedbetween a connection point of the second radiation booster 1106 and asecond connection point of the ground plane layer 1107.

The ground plane layer 1102 features a substantially rectangular shapehaving a short edge 1110 and a long edge 1111. In this example, thefirst radiation booster 1101 is substantially close to a first corner ofthe ground plane layer 1112 and the second radiation booster issubstantially close to a second corner of the ground plane layer 1113.Since the ground plane layer is substantially rectangular, the first andsecond corners 1112, 1113 are advantageously in common with two cornersof the ground plane rectangle associated to said ground plane layer1102. Moreover, said two corners 1112, 1113 are at opposite ends of theshort edge of the ground plane layer 1110 (which coincides in thisexample with a short side of the ground plane rectangle).

In the radiation structure 1100, the first radiation booster 1101 isarranged substantially close to the short edge 1110, while the secondradiation booster 1105 is arranged substantially close to the long edge1111. The short edge 1110 and the long edge 1111 are advantageouslyperpendicular and meet at the corner 1113 of the ground plane layer1102.

A radiating structure such as that in FIG. 11a may be particularlyinteresting when it is necessary to achieve higher isolation between thetwo internal ports of the radiating structure. The enhancement inisolation is due not only to the separation between the two radiationboosters (which is maximized along the short edge of the ground planelayer), but also to their relative orientation with respect to the edgesof the ground plane layer (which may excite two radiation modes on theground plane layer having substantially orthogonal polarizations).

FIG. 11b shows a radiating structure 1150 similar to that of FIG. 11a ,but in which its ground plane layer 1152 has been modified with respectto that in FIG. 11a to include two cut-out portions in which metal hasbeen removed from the ground plane layer 1152. A first cut-out portion1153 has been provided where the ground plane layer 1102 had its firstcorner 1112, while a second cut-out portion 1154 has been provided wherethe ground plane layer 1102 had its second corner 1113.

Despite the fact that the ground plane layer 1152 is irregularly shapedcompared to the rectangular ground plane layer 1102), it has a groundplane rectangle 1151 equal to that associated to the ground plane layer1102.

The first radiation booster 1101 can now be provided on the firstcut-out portion 1153, while the second radiation booster 1105 can beprovided on the second cut-out portion 1154. That is, with respect tothe example in FIG. 11a , the radiation boosters 1101, 1105 have beenreceded towards the inside of the ground plane rectangle 1151, so thatthe orthogonal projection of the first and second radiation booster1101, 1105 on the plane containing the ground plane layer 1152 iscompletely inside the perimeter of the ground plane rectangle 1151. Sucha ground plane layer and arrangement of the radiation boosters withrespect to the ground plane layer are advantageous to facilitate theintegration of the radiating structure within a particular handheld orportable wireless device.

In FIG. 12, it is presented another example of a radiating structure fora radiating system according to the present invention. The radiatingstructure 1200 comprises two radiation boosters: a first radiationbooster 1201 and a second ration booster 1203, each again comprising aconductive part. The radiating structure 1200 further comprises a groundplane layer 1202 (shown only partially in FIG. 12), inscribed in aground plane rectangle 1204. The ground plane rectangle 1204 has a shortside 1205 and a long side 1206.

The first radiation booster 1201 is arranged substantially close to saidshort side 1205, and the second radiation booster 1203 is arrangedsubstantially close to said long side 1206. Moreover, the first andsecond radiation boosters 1201, 1203 are also substantially close to afirst corner of the ground plane rectangle 1204, said corner beingdefined by the intersection of said short side 1205 and said long side1206.

In this particular case, the first radiation booster 1201 protrudesbeyond the short side 1205 of the ground plane rectangle 1204, so thatthe orthogonal projection of the first radiation booster 1201 on theplane containing the ground plane layer 1202 is outside the ground planerectangle 1204. On the other hand, the second radiation booster 1203 isarranged on a cut-out portion of the ground plane layer 1202, so thatthe orthogonal projection of the second radiation booster 1203 on saidplane containing the ground plane layer 1202 does not overlap the groundplane layer. Moreover, said projection is completely inside theperimeter of the ground plane rectangle 1204.

However, in another example both the first and the second radiationboosters could have been arranged on cut-out portions of the groundplane layer, so that the radiation boosters are at least partially, oreven completely, inside the perimeter of the ground plane rectangleassociated to the ground plane layer of a radiating structure. And yetin another example, both the first and the second radiation boosterscould have been arranged at least partially, or even completely,protruding beyond a side of said ground plane rectangle.

The radiating structure 1200 may be advantageous to facilitate theinterconnection of the radiation boosters 1201, 1203 to a radiofrequencysystem, since the connection points of said radiation boosters (notindicated in FIG. 12) are much closer to each other, that they are forexample in the radiating structures of FIG. 11.

FIG. 13 presents another example of a radiating structure comprising tworadiation boosters, in which one radiation booster is arranged one ontop of the other radiation booster forming a stacked configuration.

The radiating structure 1300 comprises a first and a second radiationbooster 1301, 1305 and a ground plane layer 1302. The first radiationbooster 1301 comprises a substantially planar conducting put having apolygonal shape (in this example a square shape) and a first connectionpoint 1303 located substantially on the perimeter of said conductingpart. The second radiation booster 1305 also comprises a substantiallyplanar conducting part having a polygonal shape and a second connectionpoint 1306 located substantially on the perimeter of said conductingpart. Said first and second connection points 1303, 1306 define togetherwith a connection point of the ground plane layer 1302 (not shown in thefigure) a first and a second internal port of the radiating structure1300.

In the example of the figure, the shape and dimensions of the tworadiation boosters 1301, 1305 are substantially the same, although inother examples the boosters may have different shapes and/or sizes,although preferably they will be substantially planar.

The first radiation booster 1301 is substantially coplanar to the groundplane layer 1302 of the radiating structure 1300, and is arranged withrespect to said ground plane layer 1302 such that the first radiationbooster 1301 is substantially close to a short edge 1304 of the groundplane layer 1302 and protrudes beyond said short edge 1304.

The second radiation booster 1305 is advantageously located at a certainheight h above the first radiation booster 1301, such that theorthogonal projection of the second radiation booster 1305 on the planecontaining the ground plane layer 1302 overlaps a substantial portion ofthe orthogonal projection of the first radiation booster 1301 on saidplane. A substantial portion may preferably refer to at least 50%, 60%,75% or 90% of the area of the orthogonal projection of the firstradiation booster 1301. In the example of the figure, the portionoverlapped corresponds to 100% of the area of the orthogonal projectionof the first radiation booster 1301. This overlapping between theradiation boosters of a radiating structure is advantageous forachieving a very compact arrangement.

Furthermore, in order to facilitate the integration of the first andsecond boosters 1301, 1305, the height h is preferably not larger than a2% of the free-space wavelength corresponding to the lowest frequency ofthe first frequency region of operation of the radiating systemcomprising the radiating structure 1300. In this example, said height his about 5 mm, although in other examples it could be even smaller.

FIG. 14 provides three examples of radiating structures for a radiatingsystem capable of operating in a first and in a second frequency regionaccording to the present invention that combine a radiation boostercomprising a conductive part with another radiation booster comprising agap defined in the ground plane layer of the radiating structure. Inparticular, in FIG. 14a a radiating structure 1400 comprises a firstradiation booster 1401 and a second radiation booster 1405. Bothradiation boosters 1401, 1405 cooperate with a ground plane layer 1402(shown partially in the figure).

The first radiation booster 1401 comprises a conducting part and issimilar to the radiation boosters already described in connection withthe example of FIG. 4. That is, the conductive part of the firstradiation booster 1401 features a polyhedral shape comprising six faces.Moreover, since in this case said six faces are substantially square,said conductive part is a cube. Said first booster comprises aconnection point 1403 that defines together with a first connectionpoint of the ground plane layer 1404 a first internal port of theradiating structure.

The second radiation booster 1405 comprises a gap defined in the groundplane layer 1402. Said gap is delimited by a plurality of segments (moreprecisely, 3 segments in the examples shown in FIG. 14) defining acurve, which in this case is open as the curve intersects the perimeterof the ground plane layer 1402 (in particular a long edge 1409 of saidground plane layer 1402). Furthermore, the gap of the second radiationbooster 1405 features a polygonal shape, which in this example issubstantially square. This second radiation booster 1405 comprises aconnection point 1406 located at a first point along said curve. Asecond connection point of the ground plane layer 1407 is located at asecond point along said curve, said second point being different fromsaid first point. A second internal port of the radiating structure 1400is defined between the connection point 1406 and the second connectionpoint of the ground plane layer 1407.

In FIG. 14a , the first radiation booster 1401 is arranged with respectto the ground plane layer 1402 so that the upper and bottom faces of thefirst radiation booster 1401 are substantially parallel to the groundplane layer 1402. Moreover, the bottom face of the first radiationbooster 1401 is advantageously coplanar to the ground plane layer 1402.Thus, the first radiation booster 1401 is substantially coplanar to thesecond radiation booster 1405.

In the radiating structure 1400, the first radiation booster 1401protrudes beyond a short edge 1408 of the ground plane layer 1402, andis located substantially close to said short edge 1408, and moreprecisely substantially close to an end of said short edge 1408. Thesecond radiation booster 1405 is located substantially close to a longedge 1409 of the ground plane layer 1402, said long edge 1409 beingsubstantially perpendicular to said short edge 1408. More specifically,the second radiation booster 1405 is located near an end of the longedge 1409, said end being in common with an end of the short side 1408.

In accordance with an aspect of the present invention, a maximum size ofeach of the first and second radiation boosters 1401, 1405 isadvantageously smaller than 1/30 times the free-space wavelengthcorresponding to the lowest frequency of the first frequency region ofoperation of the radiating structure 1400. Furthermore in this example,at least the first radiation booster 1401 has a maximum size smallerthan 1/30 times the free-space wavelength corresponding to the lowestfrequency of the second frequency region of operation of the radiatingstructure 1400.

The very small dimensions of the first and second radiation boosters1401, 1405 result in the radiating structure 1400 having at each of thefirst and second internal ports a first resonance frequency at afrequency much higher than the frequencies of the first frequencyregion. According to the present invention, the ratio between the firstresonance frequency of the radiating structure 1400 measured at each ofthe first and second internal ports (in absence of a radiofrequencysystem connected to them) and the highest frequency of the firstfrequency region is advantageously larger than 3.5. Said first resonancefrequency at each of the first and second internal ports of theradiating structure 1400 is also at a frequency much higher than thefrequencies of the second frequency region.

With such small first and second radiation boosters 1401, 1405, theinput impedance of the radiating structure 1400 measured at the firstinternal port features an important capacitive component within thefrequencies of the first and second frequency regions, and the secondinternal port features an important inductive component within thefrequencies of the first and second frequency regions.

The radiating structure 1430 shown in FIG. 14b is a modification of theradiating structure 1400 of FIG. 14a , in which the arrangement of thefirst and second radiation boosters 1401, 1405 with respect to theground plane layer 1402 is different.

In particular, the second radiation booster 1405 has been translated androtated with respect to the case shown in FIG. 14a . The secondradiation booster 1405 is now located substantially close to the shortedge 1408 of the ground plane layer 1402, and more preciselysubstantially close to an end of said short edge 1408. Given that thefirst radiation booster 1401 is also located substantially close to saidend of the short edge 1408, the first and second radiation boosters1401, 1405 are arranged near a same corner of the ground plane layer1402, which facilitates the interconnection of the radiation boosterswith a radiofrequency system.

Furthermore, the second radiation booster 1405 has undergone a 90 degreeclockwise rotation, so that the curve delimiting the gap of said secondradiation booster 1405 intersects now the short edge 1408 of the groundplane layer 1402. Such an orientation makes it possible for the secondradiation booster 1405 to excite a radiation mode on the ground planelayer 1402 having a polarization substantially orthogonal to thepolarization of the radiation mode excited on the ground plane layer1402 by the first radiation booster 1401.

Referring now to FIG. 14c , it is shown another example of a radiatingstructure that constitutes a further modification of the two previousones. More specifically, the position of the first radiation booster1401 has been modified with respect to the position it had in the caseof FIG. 14b , so that the first radiation booster 1401 has a projectionon the plane containing the ground plane layer 1402 that is completelywithin the projection of the second radiation booster 1405 on said sameplane. Moreover, the orthogonal projection of the first and secondradiation boosters 1401, 1405 on said plane containing the ground planelayer 1402 is completely inside the perimeter of the ground planerectangle 1462 associated to the ground plane layer 1402. Such anarrangement leads to very compact solutions.

The first radiation booster 1401 is advantageously embedded within thesecond radiation booster 1405, because at least a part of a firstbooster box associated to the first radiation booster 1401 is containedwithin a second booster box 1461 associated to the second radiationbooster 1405. In this particular example, the first booster boxcoincides with the external area of the first radiation booster 1401,while the second booster box 1461 is a two-dimensional entity definedaround the gap of the second radiation booster 1405. The bottom face ofthe first booster box is thus contained within the second booster box1461.

FIG. 15 shows another radiating structure 1500 for a radiating systemcapable of operating in a first and in a second frequency region of theelectromagnetic spectrum when an appropriate radiofrequency system isconnected to said radiating structure 1500.

As in the previous examples, the radiation structure 1500 comprises asubstantially rectangular ground plane layer 1502 and a first radiationbooster 1501. However, there is no second radiation booster. That is,the radiating structure 1500 has only one radiation booster.

The first radiation booster 1501 protrudes beyond the ground plane layer1502 (i.e., there is no ground plane in the orthogonal projection of theradiation booster 1501 onto the plane containing the ground plane layer1502). Moreover, said first radiation booster 1501 is advantageouslylocated substantially close to a corner of the ground plane layer 1502,said corner being defined by the intersection of a short edge 1505 and along edge 1506 of the ground plane layer 1502.

The first radiation booster 1501 comprises a connection point 1503,which defines together with a connection point of the ground plane layer1504 an internal port of the radiating structure 1500.

In this example, the first radiation booster 1501 (i.e., a sameradiation booster) in cooperation with a radiofrequency systemadvantageously excites at least two different radiation modes on theground plane layer 1502 responsible for the operation of the resultingradiating system in said first and second frequency regions of theelectromagnetic spectrum.

FIG. 16 shows an example of a radiofrequency system suitable forinterconnection with the radiating structure of FIG. 15, Theradiofrequency system 1600 comprises a first diplexer 1603 to separatethe electrical signals of a first and a second frequency regions ofoperation of a radiating system, a first matching network 1605 toprovide impedance matching in said first frequency region, a secondmatching network 1606 to provide impedance matching in said secondfrequency region, and a second diplexer 1604 to recombine the electricalsignals of said first and second frequency regions.

Each of the first and second matching networks 1605, 1606 may be as inany of the examples of matching networks described in connection withFIG. 3.

The first diplexer 1603 is connected to a first port 1601, while thesecond diplexer 1604 is connected to a second port 1602. In a radiatingsystem, an internal port of a radiating structure (such as for instancethe internal port of the radiating structure 1500) may be connected tosaid first port 1601, while an external port of the radiating system maybe connected to said second port 1602.

The use of diplexers in the radiofrequency system is advantageous toseparate the electrical signals of different frequency regions andtransform the input impedance characteristics in each frequency regionindependently from the others.

Even though that in the illustrative examples described above inconnection with the figures some particular designs of radiationboosters have been used, many other designs of radiation boosters havingfor example different shape and/or dimensions could have been equallyused in the radiating structures.

In that sense, although the first and second radiation boosters in FIGS.4, 11, and 12, and the first radiation booster in FIGS. 14 and 15, havea volumetric geometry, other designs of substantially planar radiationboosters could have been used instead.

Also, even though that some examples of radiating structures (such asfor instance, but not limited to, those in FIG. 4, 11, 12 or 15) havebeen described as comprising radiation boosters having a conductivepart, other possible examples could have been constructed usingradiation boosters comprising a gap defined in the ground plane layer ofthe radiating structure.

In the same way, despite the fact that the first and second radiationboosters in FIGS. 4 and 11-13 have been chosen to be equal in topology(i.e., a planar versus a volumetric geometry), shape and size, theycould have been selected to have different topology, shape and/or size,while preserving for example the relative location of the radiationboosters with respect to each other and with respect to the ground planelayer.

1-16. (canceled)
 17. A radiation booster comprising: a substantiallyplanar conductive element defined by a polygonal contour, the radiationbooster being configured to be part of a radiating structure of aradiating system that further includes a radiofrequency system and anexternal port, wherein: the radiating structure further comprises aground plane layer capable of supporting at least two radiation modes,the ground plane layer including a connection point, the radiationbooster being substantially coplanar with the ground plane layer; theradiation booster couples electromagnetic energy from/to the groundplane layer, the radiation booster including a connection point, aninternal port of the radiation booster being defined between theconnection point of the radiation booster and the connection point ofthe ground plane layer; the radiating system operates at first andsecond frequency regions, the second frequency region having a lowestfrequency higher than a highest frequency of the first frequency region;a first resonance frequency at the internal port of the radiationbooster when the radiofrequency system included in the radiating systemis disconnected, is above the first frequency region of the radiatingsystem; and a first ground plane layer radiation mode is responsible foroperation in the first frequency region, and a second ground plane layerradiation mode is responsible for operation in the second frequencyregion.
 18. The radiation booster of claim 17, wherein a ratio betweenthe first resonance frequency and the highest frequency of the firstfrequency region is greater than 3.0.
 19. The radiation booster of claim17, wherein a ratio between the first resonance frequency and thehighest frequency of the first frequency region is greater than 3.4. 20.The radiation booster of claim 17, wherein a ratio between the firstresonance frequency and the highest frequency of the first frequencyregion is greater than 3.8.
 21. The radiation booster of claim 17,wherein a ratio between the first resonance frequency and the highestfrequency of the first frequency region is greater than 4.0.
 22. Theradiation booster of claim 17, wherein a ratio between the firstresonance frequency and the highest frequency of the first frequencyregion is greater than 4.2.
 23. The radiation booster of claim 17,wherein a ratio between the first resonance frequency and the highestfrequency of the first frequency region is greater than 4.4.
 24. Theradiation booster of claim 17, wherein a ratio between the firstresonance frequency and the highest frequency of the first frequencyregion is greater than 4.6.
 25. The radiation booster of claim 17,wherein a ratio between the first resonance frequency and the highestfrequency of the first frequency region is greater than 4.8.
 26. Theradiation booster of claim 17, wherein a ratio between the firstresonance frequency and the highest frequency of the first frequencyregion is greater than 5.0.
 27. The radiation booster of claim 17,wherein a ratio between the first resonance frequency and the highestfrequency of the first frequency region is greater than 5.4.
 28. Theradiation booster of claim 17, wherein a ratio between the firstresonance frequency and the highest frequency of the first frequencyregion is greater than 5.8.
 29. The radiation booster of claim 17,wherein a ratio between the first resonance frequency and the highestfrequency of the first frequency region is greater than 6.0.
 30. Theradiation booster of claim 17, wherein an input impedance of theradiating structure features a reactive behavior within the firstfrequency region.
 31. The radiation booster of claim 30, wherein theinput impedance of the radiating structure features a capacitivebehavior within the first frequency region.
 32. The radiation booster ofclaim 17, wherein an input impedance of the radiating structure featuresa reactive behavior within the first and second frequency regions. 33.The radiation booster of claim 17, wherein a frequency region ofoperation of the radiating system is contained within one of thefollowing: 824-960 MHz, 1710-2170 MHz, 2.4-2.5 GHz, and 3.4-3.6 GHz. 34.The radiation booster of claim 17, wherein a first frequency region iscontained within the frequency range 824-960 MHz and the secondfrequency region is contained within the frequency range 1710-2170 MHzor 2.4-2.5 GHz.
 35. The radiation booster of claim 34, wherein thesecond frequency region of operation is contained within the frequencyrange 1710-2170 MHz.
 36. The radiation booster of claim 17, wherein theradiating system operates in one or more cellular communicationstandards.